Method for transmitting and receiving phase noise compensation reference signal in wireless communication system and apparatus therefor

ABSTRACT

A method of transmitting, by a terminal, a phase noise compensation reference signal in a wireless communication system is discussed. The method includes determining a frequency resource and a time resource of a demodulation reference signal (DM-RS); mapping the phase noise compensation reference signal to a frequency resource and a time resource based on the determined frequency resource and the time resource of the DM-RS; and transmitting, to a base station, the phase noise compensation reference signal on the mapped frequency resource and the time resource of the phase compensation reference signal. Further, a location of a phase noise compensation reference signal symbol in the time resource is determined based on a location of a DM-RS symbol in the time resource of the DM-RS.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a Continuation of co-pending U.S. patent applicationSer. No. 16/064,340 filed on Nov. 23, 2018, which is the National Phaseof PCT International Application No. PCT/KR2017/001375 filed on Feb. 8,2017, which claims the priority benefit under 35 U.S.C. § 119(e) to U.S.Provisional Application No. 62/347,640 filed on Jun. 9, 2016, all ofwhich are hereby expressly incorporated by reference into the presentapplication.

BACKGROUND OF THE INVENTION Field of the Invention

This specification relates to a wireless communication system, and moreparticularly to a method for transmitting and receiving a Phase noiseCompensation Reference Signal (PCRS) in a wireless communication systemand an apparatus therefor.

Discussion of the Related Art

Mobile communication systems have been developed to provide voiceservices while ensuring the activity of a user. However, the mobilecommunication systems have been expanded to their regions up to dataservices as well as voice. Today, the shortage of resources is causeddue to an explosive increase of traffic, and more advanced mobilecommunication systems are required due to user's need for higher speedservices.

Requirements for a next-generation mobile communication system basicallyinclude the acceptance of explosive data traffic, a significant increaseof a transfer rate per user, the acceptance of the number ofsignificantly increased connection devices, very low end-to-end latency,and high energy efficiency. To this end, research is carried out onvarious technologies, such as dual connectivity, massive Multiple InputMultiple Output (MIMO), in-band full duplex, Non-Orthogonal MultipleAccess (NOMA), the support of a super wideband, and device networking.

SUMMARY OF THE INVENTION

An object of this specification is to provide a method for defining aPhase noise Compensation Reference Signal (PCRS) for compensating aphase noise and a Doppler impact.

Another object of this specification is to provide a method fortransmitting a PCRS in consideration of a transmission location of aDemodulation Reference Signal (DMRS).

Technical problems to be solved by the present invention are not limitedby the above-mentioned technical problems, and other technical problemswhich are not mentioned above can be clearly understood from thefollowing description by those skilled in the art to which the presentinvention pertains.

This specification provides a method for transmitting and receiving, bya user equipment (UE), a phase noise compensation reference signal(PCRS) in a wireless communication system, the method comprisingreceiving, from a base station, control information related to atransmission of a downlink data, wherein the control informationincludes at least one of a precoding scheme related to the downlinkdata, a number of transmission ranks, or a modulation and coding scheme(MCS) level; checking a transmission location of a demodulationreference signal (DM-RS) for demodulating the downlink data based on thereceived control information; and receiving, from the base station, thePCRS on at least one symbol after a transmission symbol of the DM-RSconsidering the checked transmission location of the DM-RS.

In this specification, when the DM-RS is transmitted on the samefrequency as the frequency, on which the PCRS is transmitted, as aresult of checking the transmission location of the DM-RS, a sequence ofthe PCRS equally uses a sequence of the DM-RS.

In this specification, when the DM-RS is not transmitted on the samefrequency as the frequency, on which the PCRS is transmitted, as aresult of checking the transmission location of the DM-RS, a sequence ofthe PCRS equally uses a sequence of a DM-RS transmitted on a frequencyclosest to the frequency on which the PCRS is transmitted.

In this specification, the PCRS is transmitted on one or more antennaports.

In this specification, when the PCRS is transmitted on multiple antennaports, frequencies of PCRSs transmitted on different antenna ports aredifferent from each other.

In this specification, when the PCRS is transmitted on two antennaports, a PCRS transmitted on a first antenna port is transmitted at afrequency corresponding to a subcarrier index #5, and a PCRS transmittedon a second antenna port is transmitted at a frequency corresponding toa subcarrier index #6.

In this specification, a sequence of the PCRS is generated using a goldsequence.

This specification provides a user equipment (UE) for transmitting andreceiving a phase noise compensation reference signal (PCRS) in awireless communication system, the UE comprising a radio frequency (RF)unit for transmitting and receiving a radio signal; and a processor forcontrolling the RF unit, wherein the processor controls to receive, froma base station, control information related to a transmission of adownlink data, wherein the control information includes at least one ofa precoding scheme related to the downlink data, a number oftransmission ranks, or a modulation and coding scheme (MCS) level; checka transmission location of a demodulation reference signal (DM-RS) fordemodulating the downlink data based on the received controlinformation; and receive, from the base station, the PCRS on at leastone symbol after a transmission symbol of the DM-RS considering thechecked transmission location of the DM-RS.

In this specification, when the DM-RS is transmitted on the samefrequency as the frequency, on which the PCRS is transmitted, as aresult of checking the transmission location of the DM-RS, the processorcontrols to enable a sequence of the PCRS to equally use a sequence ofthe DM-RS.

In this specification, when the DM-RS is not transmitted on the samefrequency as the frequency, on which the PCRS is transmitted, as aresult of checking the transmission location of the DM-RS, the processorcontrols to enable a sequence of the PCRS to equally use a sequence of aDM-RS transmitted on a frequency closest to the frequency on which thePCRS is transmitted.

This specification has an effect capable of minimizing a phase noise ora Doppler impact by transmitting a PCRS in consideration of atransmission location of a demodulation reference signal (DMRS).

This specification has an advantage of improving a performance of areference signal (RS) by defining a PCRS so that a PCRS is transmittedthrough multiple frequency axes.

Effects obtainable from the present invention are not limited by theabove-mentioned effect, and other effects which are not mentioned abovecan be clearly understood from the following description by thoseskilled in the art to which the present invention pertains.

BRIEF DESCRIPTION OF THE DRAWINGS

The accompanying drawings that are included provide a furtherunderstanding of the invention and are incorporated in and constitute apart of this specification, illustrate embodiments of the invention andtogether with the description serve to explain various principles of theinvention.

FIG. 1 illustrates a structure of a radio frame in a wirelesscommunication system to which the present invention is applicable.

FIG. 2 illustrates a resource grid for one downlink slot in a wirelesscommunication system to which the present invention is applicable.

FIG. 3 illustrates a structure of a downlink subframe in a wirelesscommunication system to which the present invention is applicable.

FIG. 4 illustrates a structure of an uplink subframe in a wirelesscommunication system to which the present invention is applicable.

FIG. 5 illustrates a reference signal pattern mapped to a downlinkresource block pair in a wireless communication system to which thepresent invention is applicable.

FIG. 6 illustrates an example of a power spectral density of anoscillator.

FIG. 7 illustrates an example of a U-shaped Doppler spectrum.

FIG. 8 illustrates an example of reduced angular spread.

FIG. 9 illustrates an example of a Doppler spectrum in narrowbeamforming.

FIG. 10 illustrates an example of a downlink synchronization signalservice area of a base station.

FIG. 11 illustrates an example of an mmWave frame structure.

FIG. 12 illustrates an example of an OVSF code tree structure.

FIG. 13 illustrates an example of distribution of UEs.

FIG. 14 illustrates an example of a location on time and frequency axesof a PCRS proposed by this specification.

FIG. 15 illustrates another example of a location on time and frequencyaxes of a PCRS proposed by this specification.

FIG. 16 illustrates another example of a location on time and frequencyaxes of a PCRS proposed by this specification.

FIG. 17 illustrates another example of a location on time and frequencyaxes of a PCRS proposed by this specification.

FIG. 18 is a flow chart illustrating an example of a method fortransmitting and receiving a PCRS proposed by this specification.

FIG. 19 is a block diagram illustrating a configuration of a wirelesscommunication device to which the present invention is applicable.

DETAILED DESCRIPTION OF THE EMBODIMENTS

Hereafter, preferred embodiments of the present invention will bedescribed in detail with reference to the accompanying drawings. Adetailed description to be disclosed hereinbelow together with theaccompanying drawing is to describe embodiments of the present inventionand not to describe a unique embodiment for carrying out the presentinvention. The detailed description below includes details in order toprovide a complete understanding. However, those skilled in the art knowthat the present invention can be carried out without the details.

In some cases, in order to prevent a concept of the present inventionfrom being ambiguous, known structures and devices may be omitted or maybe illustrated in a block diagram format based on core function of eachstructure and device.

In the specification, a base station means a terminal node of a networkdirectly performing communication with a terminal. In the presentdocument, specific operations described to be performed by the basestation may be performed by an upper node of the base station in somecases. That is, it is apparent that in the network constituted bymultiple network nodes including the base station, various operationsperformed for communication with the terminal may be performed by thebase station or other network nodes other than the base station. A basestation (BS) may be generally substituted with terms such as a fixedstation, Node B, evolved-NodeB (eNB), a base transceiver system (BTS),an access point (AP), and the like. Further, a ‘terminal’ may be fixedor movable and be substituted with terms such as user equipment (UE), amobile station (MS), a user terminal (UT), a mobile subscriber station(MSS), a subscriber station (SS), an advanced mobile station (AMS), awireless terminal (WT), a Machine-Type Communication (MTC) device, aMachine-to-Machine (M2M) device, a Device-to-Device (D2D) device, andthe like.

Hereinafter, a downlink means communication from the base station to theterminal and an uplink means communication from the terminal to the basestation. In the downlink, a transmitter may be a part of the basestation and a receiver may be a part of the terminal. In the uplink, thetransmitter may be a part of the terminal and the receiver may be a partof the base station.

Specific terms used in the following description are provided to helpappreciating the present invention and the use of the specific terms maybe modified into other forms within the scope without departing from thetechnical spirit of the present invention.

The following technology may be used in various wireless access systems,such as code division multiple access (CDMA), frequency divisionmultiple access (FDMA), time division multiple access (TDMA), orthogonalfrequency division multiple access (OFDMA), single carrier-FDMA(SC-FDMA), non-orthogonal multiple access (NOMA), and the like. The CDMAmay be implemented by radio technology universal terrestrial radioaccess (UTRA) or CDMA2000. The TDMA may be implemented by radiotechnology such as Global System for Mobile communications (GSM)/GeneralPacket Radio Service (GPRS)/Enhanced Data Rates for GSM Evolution(EDGE). The OFDMA may be implemented as radio technology such as IEEE802.11(Wi-Fi), IEEE 802.16(WiMAX), IEEE 802-20, E-UTRA (Evolved UTRA),and the like. The UTRA is a part of a universal mobile telecommunicationsystem (UMTS). 3rd generation partnership project (3GPP) long termevolution (LTE) as a part of an evolved UMTS (E-UMTS) using evolved-UMTSterrestrial radio access (E-UTRA) adopts the OFDMA in a downlink and theSC-FDMA in an uplink. LTE-advanced (A) is an evolution of the 3GPP LTE.

The embodiments of the present invention may be based on standarddocuments disclosed in at least one of IEEE 802, 3GPP, and 3GPP2 whichare the wireless access systems. That is, steps or parts which are notdescribed to definitely show the technical spirit of the presentinvention among the embodiments of the present invention may be based onthe documents. Further, all terms disclosed in the document may bedescribed by the standard document.

3GPP LTE/LTE-A is primarily described for clear description, buttechnical features of the present invention are not limited thereto.

General Wireless Communication System to which an Embodiment of thePresent Invention May be Applied

FIG. 1 shows the structure of a radio frame in a wireless communicationsystem to which an embodiment of the present invention may be applied.

3GPP LTE/LTE-A support a type 1 radio frame structure capable of beingapplied to frequency division duplex (FDD) and a type 2 radio framestructure capable of being applied to time division duplex (TDD).

In FIG. 1, the size of the radio frame in a time domain is expressed ina multiple of a time unit “T_s=1/(15000*2048).” Downlink and uplinktransmission includes a radio frame having an interval ofT_f=307200*T_s=10 ms.

FIG. 1(a) illustrates the type 1 radio frame structure. The type 1 radioframe may be applied to both full duplex FDD and half duplex FDD.

The radio frame includes 10 subframes. One radio frame includes 20 slotseach having a length of T_slot=15360*T_s=0.5 ms. Indices 0 to 19 areassigned to the respective slots. One subframe includes two contiguousslots in the time domain, and a subframe i includes a slot 2 i and aslot 2 i+1. The time taken to send one subframe is called a transmissiontime interval (TTI). For example, the length of one subframe may be 1ms, and the length of one slot may be 0.5 ms.

In FDD, uplink transmission and downlink transmission are classified inthe frequency domain. There is no restriction to full duplex FDD,whereas a UE is unable to perform transmission and reception at the sametime in a half duplex FDD operation.

One slot includes a plurality of orthogonal frequency divisionmultiplexing (OFDM) symbols in the time domain and includes a pluralityof resource blocks (RBs) in the frequency domain. An OFDM symbol is forexpressing one symbol period because 3GPP LTE uses OFDMA in downlink.The OFDM symbol may also be called an SC-FDMA symbol or a symbol period.The resource block is a resource allocation unit and includes aplurality of contiguous subcarriers in one slot.

FIG. 1(b) shows the type 2 radio frame structure.

The type 2 radio frame structure includes 2 half frames each having alength of 153600*T_s=5 ms. Each of the half frames includes 5 subframeseach having a length of 30720*T_s=1 ms.

In the type 2 radio frame structure of a TDD system, an uplink-downlinkconfiguration is a rule showing how uplink and downlink are allocated(or reserved) with respect to all of subframes.

Table 1 shows the uplink-downlink configuration.

TABLE 1 DOWN- UPLINK- LINK- DOWN- TO-UPLINK LINK SWITCH- CON- POINTFIGU- PERIO- SUBFRAME NUMBER RATION DICITY 0 1 2 3 4 5 6 7 8 9 0 5 ms DS U U U D S U U U 1 5 ms D S U U D D S U U D 2 5 ms D S U D D D S U D D3 10 ms  D S U U U D D D D D 4 10 ms  D S U U D D D D D D 5 10 ms  D S UD D D D D D D 6 5 ms D S U U U D S U U D

Referring to Table 1, “D” indicates a subframe for downlinktransmission, “U” indicates a subframe for uplink transmission, and “S”indicates a special subframe including the three fields of a downlinkpilot time slot (DwPTS), a guard period (GP), and an uplink pilot timeslot (UpPTS) for each of the subframes of the radio frame.

The DwPTS is used for initial cell search, synchronization or channelestimation by a UE. The UpPTS is used for an eNB to perform channelestimation and for a UE to perform uplink transmission synchronization.The GP is an interval for removing interference occurring in uplink dueto the multi-path delay of a downlink signal between uplink anddownlink.

Each subframe i includes the slot 2 i and the slot 2 i+1 each having“T_slot=15360*T_s=0.5 ms.”

The uplink-downlink configuration may be divided into seven types. Thelocation and/or number of downlink subframes, special subframes, anduplink subframes are different in the seven types.

A point of time changed from downlink to uplink or a point of timechanged from uplink to downlink is called a switching point.Switch-point periodicity means a cycle in which a form in which anuplink subframe and a downlink subframe switch is repeated in the samemanner. The switch-point periodicity supports both 5 ms and 10 ms. Inthe case of a cycle of the 5 ms downlink-uplink switching point, thespecial subframe S is present in each half frame. In the case of thecycle of the 5 ms downlink-uplink switching point, the special subframeS is present only in the first half frame.

In all of the seven configurations, No. 0 and No. 5 subframes and DwPTSsare an interval for only downlink transmission. The UpPTSs, thesubframes, and a subframe subsequent to the subframes are always aninterval for uplink transmission.

Both an eNB and a UE may be aware of such uplink-downlink configurationsas system information. The eNB may notify the UE of a change in theuplink-downlink allocation state of a radio frame by sending only theindex of configuration information whenever uplink-downlinkconfiguration information is changed. Furthermore, the configurationinformation is a kind of downlink control information. Like schedulinginformation, the configuration information may be transmitted through aphysical downlink control channel (PDCCH) and may be transmitted to allof UEs within a cell in common through a broadcast channel as broadcastinformation.

Table 2 shows a configuration (i.e., the length of a DwPTS/GP/UpPTS) ofthe special subframe.

TABLE 2 Normal cyclic prefix in downlink UpPTS Extended cyclic prefix indownlink Normal UpPTS cyclic Extended Normal Special prefix cycliccyclic Extended subframe in prefix prefix in cyclic prefix configurationDwPTS uplink in uplink DwPTS uplink in uplink 0  6592 · T_(s) 2192 ·T_(s) 2560 · T_(s)  7680 · T_(s) 2192 · T_(s) 2560 · T_(s) 1 19760 ·T_(s) 20480 · T_(s) 2 21952 · T_(s) 23040 · T_(s) 3 24144 · T_(s) 25600· T_(s) 4 26336 · T_(s)  7680 · T_(s) 4384 · T_(s) 5120 · T_(s) 5  6592· T_(s) 4384 · T_(s) 5120 · T_(s) 20480 · T_(s) 6 19760 · T_(s) 23040 ·T_(s) 7 21952 · T_(s) — — — 8 24144 · T_(s) — — —

The structure of the radio frame according to the example of FIG. 1 isonly one example. The number of subcarriers included in one radio frame,the number of slots included in one subframe, and the number of OFDMsymbols included in one slot may be changed in various manners.

FIG. 2 is a diagram illustrating a resource grid for one downlink slotin the wireless communication system to which the present invention canbe applied.

Referring to FIG. 2, one downlink slot includes the plurality of OFDMsymbols in the time domain. Herein, it is exemplarily described that onedownlink slot includes 7 OFDM symbols and one resource block includes 12subcarriers in the frequency domain, but the present invention is notlimited thereto.

Each element on the resource grid is referred to as a resource elementand one resource block includes 12×7 resource elements. The number ofresource blocks included in the downlink slot, NDL is subordinated to adownlink transmission bandwidth.

A structure of the uplink slot may be the same as that of the downlinkslot.

FIG. 3 illustrates a structure of a downlink subframe in the wirelesscommunication system to which the present invention can be applied.

Referring to FIG. 3, a maximum of three former OFDM symbols in the firstslot of the sub frame is a control region to which control channels areallocated and residual OFDM symbols is a data region to which a physicaldownlink shared channel (PDSCH) is allocated. Examples of the downlinkcontrol channel used in the 3GPP LTE include a Physical Control FormatIndicator Channel (PCFICH), a Physical Downlink Control Channel (PDCCH),a Physical Hybrid-ARQ Indicator Channel (PHICH), and the like.

The PFCICH is transmitted in the first OFDM symbol of the subframe andtransports information on the number (that is, the size of the controlregion) of OFDM symbols used for transmitting the control channels inthe subframe. The PHICH which is a response channel to the uplinktransports an Acknowledgement (ACK)/Not-Acknowledgement (NACK) signalfor a hybrid automatic repeat request (HARQ). Control informationtransmitted through a PDCCH is referred to as downlink controlinformation (DCI). The downlink control information includes uplinkresource allocation information, downlink resource allocationinformation, or an uplink transmission (Tx) power control command for apredetermined terminal group.

The PDCCH may transport A resource allocation and transmission format(also referred to as a downlink grant) of a downlink shared channel(DL-SCH), resource allocation information (also referred to as an uplinkgrant) of an uplink shared channel (UL-SCH), paging information in apaging channel (PCH), system information in the DL-SCH, resourceallocation for an upper-layer control message such as a random accessresponse transmitted in the PDSCH, an aggregate of transmission powercontrol commands for individual terminals in the predetermined terminalgroup, a voice over IP (VoIP). A plurality of PDCCHs may be transmittedin the control region and the terminal may monitor the plurality ofPDCCHs. The PDCCH is constituted by one or an aggregate of a pluralityof continuous control channel elements (CCEs). The CCE is a logicalallocation wise used to provide a coding rate depending on a state of aradio channel to the PDCCH. The CCEs correspond to a plurality ofresource element groups. A format of the PDCCH and a bit number ofusable PDCCH are determined according to an association between thenumber of CCEs and the coding rate provided by the CCEs.

The base station determines the PDCCH format according to the DCI to betransmitted and attaches the control information to a cyclic redundancycheck (CRC) to the control information. The CRC is masked with a uniqueidentifier (referred to as a radio network temporary identifier (RNTI))according to an owner or a purpose of the PDCCH. In the case of a PDCCHfor a specific terminal, the unique identifier of the terminal, forexample, a cell-RNTI (C-RNTI) may be masked with the CRC. Alternatively,in the case of a PDCCH for the paging message, a paging indicationidentifier, for example, the CRC may be masked with a paging-RNTI(P-RNTI). In the case of a PDCCH for the system information, in moredetail, a system information block (SIB), the CRC may be masked with asystem information identifier, that is, a system information (SI)-RNTI.The CRC may be masked with a random access (RA)-RNTI in order toindicate the random access response which is a response to transmissionof a random access preamble.

EPDCCH (Enhanced PDCCH) carries the UE-specific (UE-specific) signaling.EPDCCH physical resource blocks is set to the UE-specific: located at(PRB physical resource block). In other words, as described above, thePDCCH but the first slot in the subframe to be sent in the previousmaximum of three OFDM symbols, EPDCCH may be transmitted in the resourcearea other than the PDCCH. When the My EPDCCH subframe starts (i.e.,symbol) can be set in the terminal through upper layer signaling (e.g.,RRC signaling, and so on).

EPDCCH the transport format, resource allocation, and HARQ information,transport format, resource allocation, and HARQ information, and theresource allocation associated with the SL-SCH (Sidelink Shared Channel)and PSCCH (Physical Sidelink Control Channel) associated with the UL-SCHrelated to DL-SCH It can carry information. There are multiple EPDCCH ofcan be supported, the terminal may monitor a set of EPCCH.

EPDCCH CCE is one or more of the successive advancement: may betransmitted using a (ECCE enhanced CCE), a number of ECCE per singleEPDCCH be determined for each EPDCCH format.

Each ECCE is a plurality of resource element groups: may be composed of(EREG enhanced resource element group). EREG is used to define the REmapping by the ECCE. PRB and a 16 EREG there by pairs. Except for REcarry the DMRS in each PRB pairs, all the RE is a number from 0 to 15 inorder to increase the next time in the order in which the frequencyincreases is given.

The UE may monitor the plurality of EPDCCH. For example, the UE can beone of PRB pairs within one or two EPDCCH set to monitor EPDCCHtransmission setting.

Merging the different number of ECCE being can be realized (coding rate)different code rates for EPCCH. EPCCH may use the local transmission(localized transmission), or distributed transmission (distributedtransmission), thereby PRB may be the mapping of ECCE vary within theRE.

FIG. 4 illustrates a structure of an uplink subframe in the wirelesscommunication system to which the present invention can be applied.

Referring to FIG. 4, the uplink subframe may be divided into the controlregion and the data region in a frequency domain. A physical uplinkcontrol channel (PUCCH) transporting uplink control information isallocated to the control region. A physical uplink shared channel(PUSCH) transporting user data is allocated to the data region. Oneterminal does not simultaneously transmit the PUCCH and the PUSCH inorder to maintain a single carrier characteristic.

A resource block (RB) pair in the subframe are allocated to the PUCCHfor one terminal. RBs included in the RB pair occupy differentsubcarriers in two slots, respectively. The RB pair allocated to thePUCCH frequency-hops in a slot boundary.

Reference Signal (RS)

In the wireless communication system, since the data is transmittedthrough the radio channel, the signal may be distorted duringtransmission. In order for the receiver side to accurately receive thedistorted signal, the distortion of the received signal needs to becorrected by using channel information. In order to detect the channelinformation, a signal transmitting method know by both the transmitterside and the receiver side and a method for detecting the channelinformation by using an distortion degree when the signal is transmittedthrough the channel are primarily used. The aforementioned signal isreferred to as a pilot signal or a reference signal (RS).

Recently, when packets are transmitted in most of mobile communicationsystems, multiple transmitting antennas and multiple receiving antennasare adopted to increase transceiving efficiency rather than a singletransmitting antenna and a single receiving antenna. When the data istransmitted and received by using the MIMO antenna, a channel statebetween the transmitting antenna and the receiving antenna need to bedetected in order to accurately receive the signal. Therefore, therespective transmitting antennas need to have individual referencesignals.

Reference signal in a wireless communication system can be mainlycategorized into two types. In particular, there are a reference signalfor the purpose of channel information acquisition and a referencesignal used for data demodulation. Since the object of the formerreference signal is to enable a UE (user equipment) to acquire a channelinformation in DL (downlink), the former reference signal should betransmitted on broadband. And, even if the UE does not receive DL datain a specific subframe, it should perform a channel measurement byreceiving the corresponding reference signal. Moreover, thecorresponding reference signal can be used for a measurement formobility management of a handover or the like. The latter referencesignal is the reference signal transmitted together when a base stationtransmits DL data. If a UE receives the corresponding reference signal,the UE can perform channel estimation, thereby demodulating data. And,the corresponding reference signal should be transmitted in a datatransmitted region.

The DL reference signals are categorized into a common reference signal(CRS) shared by all terminals for an acquisition of information on achannel state and a measurement associated with a handover or the likeand a dedicated reference signal (DRS) used for a data demodulation fora specific terminal. Information for demodulation and channelmeasurement may be provided by using the reference signals. That is, theDRS is used only for data demodulation only, while the CRS is used fortwo kinds of purposes including channel information acquisition and datademodulation.

The receiver side (that is, terminal) measures the channel state fromthe CRS and feeds back the indicators associated with the channelquality, such as the channel quality indicator (CQI), the precodingmatrix index (PMI), and/or the rank indicator (RI) to the transmittingside (that is, base station). The CRS is also referred to as acell-specific RS. On the contrary, a reference signal associated with afeed-back of channel state information (CSI) may be defined as CSI-RS.

The DRS may be transmitted through resource elements when datademodulation on the PDSCH is required. The terminal may receive whetherthe DRS is present through the upper layer and is valid only when thecorresponding PDSCH is mapped. The DRS may be referred to as theUE-specific RS or the demodulation RS (DMRS).

FIG. 5 illustrates a reference signal pattern mapped to a downlinkresource block pair in the wireless communication system to which thepresent invention can be applied.

Referring to FIG. 5, as a unit in which the reference signal is mapped,the downlink resource block pair may be expressed by one subframe in thetime domain×12 subcarriers in the frequency domain. That is, oneresource block pair has a length of 14 OFDM symbols in the case of anormal cyclic prefix (CP) (see FIG. 5(a)) and a length of 12 OFDMsymbols in the case of an extended cyclic prefix (CP) (see FIG. 5(b)).Resource elements (REs) represented as ‘0’, ‘1’, ‘2’, and ‘3’ in aresource block lattice mean the positions of the CRSs of antenna portindexes ‘0’, ‘1’, ‘2’, and ‘3’, respectively and resource elementsrepresented as ‘D’ means the position of the DRS.

Hereinafter, when the CRS is described in more detail, the CRS is usedto estimate a channel of a physical antenna and distributed in a wholefrequency band as the reference signal which may be commonly received byall terminals positioned in the cell. That is, the CRS is transmitted ineach subframe across a broadband as a cell-specific signal. Further, theCRS may be used for the channel quality information (CSI) and datademodulation.

The CRS is defined as various formats according to an antenna array atthe transmitter side (base station). The RSs are transmitted based onmaximum 4 antenna ports depending on the number of transmitting antennasof a base station in the 3GPP LTE system (for example, release-8). Thetransmitter side has three types of antenna arrays of three singletransmitting antennas, two transmitting antennas, and four transmittingantennas. For instance, in case that the number of the transmittingantennas of the base station is 2, CRSs for antenna #1 and antenna #2are transmitted. For another instance, in case that the number of thetransmitting antennas of the base station is 4, CRSs for antennas #1 to#4 are transmitted.

When the base station uses the single transmitting antenna, a referencesignal for a single antenna port is arrayed.

When the base station uses two transmitting antennas, reference signalsfor two transmitting antenna ports are arrayed by using a time divisionmultiplexing (TDM) scheme and/or a frequency division multiplexing (FDM)scheme. That is, different time resources and/or different frequencyresources are allocated to the reference signals for two antenna portswhich are distinguished from each other.

Moreover, when the base station uses four transmitting antennas,reference signals for four transmitting antenna ports are arrayed byusing the TDM and/or FDM scheme. Channel information measured by adownlink signal receiving side (terminal) may be used to demodulate datatransmitted by using a transmission scheme such as single transmittingantenna transmission, transmission diversity, closed-loop spatialmultiplexing, open-loop spatial multiplexing, or multi-user MIMO.

In the case where the MIMO antenna is supported, when the referencesignal is transmitted from a specific antenna port, the reference signalis transmitted to the positions of specific resource elements accordingto a pattern of the reference signal and not transmitted to thepositions of the specific resource elements for another antenna port.That is, reference signals among different antennas are not duplicatedwith each other.

A rule for mapping a CRS to a resource block is defined as follows.

$\begin{matrix}{{k = {{6\; m} + {( {v + v_{shift}} ){mod}\; 6}}}{l = \{ {{{\begin{matrix}{0,{N_{symb}^{DL} - 3}} & {{{if}\mspace{14mu} p} \in \{ {0,1} \}} \\1 & {{{if}\mspace{14mu} p} \in \{ {2,3} \}}\end{matrix}m} = 0},1,\ldots\mspace{14mu},{{{2 \cdot N_{RB}^{DL}} - {1m^{\prime}}} = {{m + N_{RB}^{\max,{DL}} - {N_{RB}^{DL}v}} = \{ {{\begin{matrix}0 & {{{if}\mspace{14mu} p} = {{0\mspace{14mu}{and}\mspace{14mu} l} = 0}} \\3 & {{{if}\mspace{14mu} p} = {{0\mspace{14mu}{and}\mspace{14mu} l} \neq 0}} \\3 & {{{if}\mspace{14mu} p} = {{1\mspace{14mu}{and}\mspace{14mu} l} = 0}} \\0 & {{{if}\mspace{14mu} p} = {{1\mspace{14mu}{and}\mspace{14mu} l} \neq 0}} \\{3( {n_{s}{mod}\; 2} )} & {{{if}\mspace{14mu} p} = 2} \\{3 + {3( {n_{s}{mod}\; 2} )}} & {{{if}\mspace{14mu} p} = 3}\end{matrix}v_{shift}} = {N_{ID}^{cell}{mod}\; 6}} }}} }} & \lbrack {{Equation}\mspace{14mu} 1} \rbrack\end{matrix}$

In Equation 1, k and l respectively denote a subcarrier index and asymbol index, and p denotes an antenna port. N_(symb) ^(DL) denotes thenumber of OFDM symbols in one downlink slot, and N_(RB) ^(DL) denotesthe number of radio resources allocated to the downlink. ns denotes aslot index, and N_(ID) ^(cell) denotes a cell ID. mod denotes a modulooperation. A position of a reference signal varies depending on a valueof v_(shift) in a frequency domain. Since v_(shift) depends on the cellID, the position of the reference signal has various frequency shiftvalues depending on the cell.

More specifically, in order to improve a channel estimation performancethrough a CRS, a position of the CRS may be shifted in a frequencydomain depending on a cell. For example, when reference signals arelocated at an interval of three subcarriers, reference signals in onecell are allocated to 3k-th subcarriers, and reference signals inanother cell are allocated to (3k+1)th subcarriers. In terms of oneantenna port, reference signals are arranged at an interval of sixresource elements in a frequency domain and are separated from areference signal allocated to another antenna port at an interval ofthree resource elements.

In a time domain, reference signals are arranged at a constant intervalstarting from a symbol index ‘0’ of each slot. A time interval isdifferently defined depending on the length of a cyclic prefix. In thecase of normal cyclic prefix, reference signals are positioned at symbolindexes ‘0’ and ‘4’ of a slot. In the case of extended cyclic prefix,reference signals are positioned at symbol indexes ‘0’ and ‘3’ of aslot. A reference signal for an antenna port that has a maximum valueamong two antenna ports is defined in one OFDM symbol. Thus, in the caseof transmission of four transmission antennas, reference signals forreference signal antenna ports ‘0’ and ‘1’ are positioned at the symbolindexes ‘0’ and ‘4’ of the slot (the symbol indexes ‘0’ and ‘3’ in thecase of extended cyclic prefix), and reference signals for antenna ports‘2’ and ‘3’ are positioned at the symbol index ‘1’ of the slot. Thepositions of the reference signals for the antenna ports ‘2’ and ‘3’ ina frequency domain are changed with each other in a second slot.

The DRS is described in more detail below. The DRS is used to demodulatedata. In the multi-input/output antenna transmission, a precoding weightused for a specific UE is used without change in order to estimate achannel combined with and corresponding to a transmission channeltransmitted from each transmission antenna when the UE has received areference signal.

The 3GPP LTE system (e.g., Release-8) supports up to four transmissionantennas, and a DRS for rank 1 beamforming is defined. The DRS for rank1 beamforming also indicates a reference signal for an antenna portindex ‘5’.

A rule of mapping the DRS to a resource block is defined as follows.Equation 2 indicates the case of the normal cyclic prefix, and Equation3 indicates the case of the extended cyclic prefix.

$\begin{matrix}{{k = {{( k^{\prime} ){mod}\; N_{sc}^{RB}} + {N_{sc}^{RB} \cdot n_{PRB}}}}{k^{\prime} = \{ {{\begin{matrix}{{4\; m^{\prime}} + v_{shift}} & {{{if}\mspace{14mu} l} \in \{ {2,3} \}} \\{{4\; m^{\prime}} + {( {2 + v_{shift}} ){mod}\; 4}} & {{{if}\mspace{14mu} l} \in \{ {5,6} \}}\end{matrix}l} = \{ {\begin{matrix}3 & {l^{\prime} = 0} \\6 & {l^{\prime} = 1} \\2 & {l^{\prime} = 2} \\5 & {l^{\prime} = 3}\end{matrix}l^{\prime}\{ {{{\begin{matrix}{0,1} & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 0} \\{2,3} & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 1}\end{matrix}m^{\prime}} = 0},1,\ldots\mspace{14mu},{{{3\; N_{RB}^{PDSCH}} - {1v_{shift}}} = {N_{ID}^{cell}{mod}\; 3}}} } } }} & \lbrack {{Equation}\mspace{14mu} 2} \rbrack \\{k = {{{( k^{\prime} ){mod}\; N_{sc}^{RB}} + {{N_{sc}^{RB} \cdot n_{PRB}}k^{\prime}}} = \{ {{\begin{matrix}{{3\; m^{\prime}} + v_{shift}} & {{{if}\mspace{14mu} l} = 4} \\{{3\; m^{\prime}} + {( {2 + v_{shift}} ){mod}\; 3}} & {{{if}\mspace{14mu} l} = 1}\end{matrix}l} = \{ {{\begin{matrix}4 & {l^{\prime} \in \{ {0,2} \}} \\1 & {l^{\prime} = 1}\end{matrix}l^{\prime}} = \{ {{{\begin{matrix}0 & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 0} \\{1,2} & {{{if}\mspace{14mu} n_{s}{mod}\; 2} = 1}\end{matrix}m^{\prime}} = 0},1,\ldots\mspace{14mu},{{{4\; N_{RB}^{PDSCH}} - {1v_{shift}}} = {N_{ID}^{cell}{mod}\; 3}}} } } }} & \lbrack {{Equation}\mspace{14mu} 3} \rbrack\end{matrix}$

In Equations 2 and 3, k and l respectively denote a subcarrier index anda symbol index, and p denotes an antenna port. N_(sc) ^(RB) denotes asize of a resource block in a frequency domain and is expressed as thenumber of subcarriers. n_(PRB) denotes the number of physical resourceblocks. N_(RB) ^(PDSCH) denotes a frequency band of a resource block forPDSCH transmission. ns denotes a slot index, and N_(ID) ^(cell) denotesa cell ID. mod denotes a modulo operation. A position of a referencesignal varies depending on a value of v_(shift) in a frequency domain.Since v_(shift) depends on the cell ID, the position of the referencesignal has various frequency shift values depending on the cell.

In an LTE-A system that is an evolved and developed form of an LTEsystem, a maximum of eight transmission antennas needs to be designed tobe supported to the downlink of the base station. Thus, RSs for up to 8transmission antennas also need to be supported. In the LTE system,since only RSs for up to four antenna ports are defined in a downlinkRS, when the base station has four or more and up to eight downlinktransmission antennas in the LTE-A system, RSs for antenna ports need tobe additionally defined and designed. The RSs for up to eighttransmission antenna ports each need to be designed as both an RS forchannel measurement and an RS for data demodulation described above.

One of important considerations in designing the LTE-A system isbackward compatibility, that is, that an LTE terminal needs to operatenormally even in the LTE-A system with unstudied ease and the systemalso needs to support the backward compatibility. In terms of the RStransmission, in a time-frequency domain in which the CRS defined in theLTE is transmitted in a whole band every subframe, RSs for up to eighttransmission antenna ports have to be additionally defined. In the LTE-Asystem, when RS patterns for up to eight transmission antennas are addedto the whole band every subframe by the same method as a CRS of anexisting LTE, RS overhead is excessively increased.

Accordingly, in the LTE-A system, a newly designed RS is roughlyclassified into two types that include an RS (CSI-RS: Channel StateInformation-RS, Channel State Indication-RS, etc.) for the purpose ofthe channel measurement for the selection of MCS, PMI, etc. and an RS(DMRS: Data Demodulation-RS) for the demodulation of data transmitted toeight transmission antennas.

The CSI-RS for the purpose of the channel measurement is characterizedin that it is designed for the main purpose of channel measurement,unlike an existing CRS that is used for both the measurement, such aschannel measurement and handover, and data demodulation. Naturally, theCSI-RS may also be used for the purpose of measurement such as handover.Since the CSI-RS is transmitted only for the purpose of obtaininginformation on a channel state, the CSI-RS may not be transmitted everysubframe unlike the CRS. In order to reduce overhead of the CSI-RS, theCSI-RS is intermittently transmitted on the time axis.

The DMRS is dedicatedly transmitted to a UE which is scheduled in acorresponding time-frequency domain for the data demodulation. Namely, aDMRS of a specific UE is transmitted only to a region in which thecorresponding UE has been scheduled, i.e., a time-frequency domain inwhich data is received.

In the LTE-A system, an eNB has to transmit CSI-RSs for all antennaports. Because the transmission of CSI-RSs for up to eight transmissionantenna ports every subframe has a disadvantage of too much overhead,the CSI-RS is not transmitted every subframe and has to beintermittently transmitted on the time axis, thereby reducing theoverhead. Namely, the CSI-RS may be transmitted periodically at aninteger multiple period of one subframe or transmitted in a specifictransmission pattern. In this case, the period or the pattern in whichthe CSI-RS is transmitted may be configured by the eNB.

In order to measure the CSI-RS, the UE needs to be aware of informationabout a transmission subframe index of the CSI-RS, a CSI-RS resourceelement (RE) time-frequency position in a transmission subframe, and aCSI-RS sequence for each CSI-RS antenna port of a cell to which the UEitself belongs.

In the LTE-A system, the eNB has to transmit the CSI-RS to each of up toeight antenna ports. Resources used for the CSI-RS transmission ofdifferent antenna ports have to be orthogonal to each other. When oneeNB transmits CSI-RSs for different antenna ports, the resources can beorthogonally allocated in the FDM/TDM scheme by mapping the CSI-RSs forthe respective antenna ports to different REs. Alternatively, theCSI-RSs for the different antenna ports may be transmitted in a CDMscheme with being mapped to mutually orthogonal codes.

When the eNB notifies information on a CSI-RS to the UE in its own cell,the eNB first has to notify the UE of information about a time-frequencyto which a CSI-RS for each antenna port is mapped. More specifically,the information includes subframe numbers to which the CSI-RS istransmitted or a period in which the CSI-RS is transmitted, a subframeoffset to which the CSI-RS is transmitted, an OFDM symbol number towhich the CSI-RS RE of a specific antenna is transmitted, a frequencyspacing, an offset or a shift value of an RE in a frequency axis, andthe like.

Phase Compensation Reference Signal (PCRS)

A PCRS is described in detail below.

DL PCRS Procedure

If the UE detects an xPDCCH with DCI format B1 or B2 in a subframe nintended for the UE, the UE receives a DL PCRS at a PCRS antenna portindicated in the DCI at the corresponding subframe.

UL PCRS Procedure

If a UE detects an xPDCCH with DCI format A1 or A2 in subframe nintended for the UE, the UE transmits UL PCRS in subframe n+4+m+1 usingone or two PCRS antenna ports which are the same as an assigned DM-RSantenna port indicated in the DCI except the following conditions(Condition 1 and Condition 2).

-   -   Condition 1: If a dual PCRS field of the detected DCI is set to        ‘1’ and the number of DM-RS ports assigned to the xPDCCH is ‘1’,        the UE transmits the UL PCRS in the subframe n+4+m+1 using the        assigned DM-RS antenna port indicated in the DCI and an        additional PCRS antenna port having the same subcarrier position        as a specific PCRS antenna port.    -   Condition 2: A relative transmit power ratio of the PCRS and the        xPUSCH is determined by a transmission scheme defined by the        following Table 3.

Table 3 indicates an example of a relative transmit power ratio of PCRSand xPUSCH on a given layer.

TABLE 3 Relative Transmit Transmission Scheme Power Ratio Single-layertransmission 3 dB Two-layer transmission 6 dB

The PCRS is described in more detail below.

The PCRS associated with the xPUSCH (1) is transmitted on an antennaport p p∈{40,41,42,43}, (2) exists and is a valid criterion for phasenoise compensation only if a xPUSCH transmission is associated with acorresponding antenna port, and (3) is transmitted only on physicalresource blocks and symbols to which a corresponding xPUSCH is mapped.

Sequence Generation

For any of antenna ports p∈{40,41,42,43}, a reference signal sequencer(m) is defined by the following Equation 4.

$\begin{matrix}{{{r(m)} = {{\frac{1}{\sqrt{2}}( {1 - {2 \cdot {c( {2\; m} )}}} )} + {j\frac{1}{\sqrt{2}}( {1 - {2 \cdot {c( {{2\; m} + 1} )}}} )}}},\mspace{20mu}{m = 0},1,\ldots\mspace{14mu},{\lfloor {N_{RB}^{\max,{UL}}/4} \rfloor - 1}} & \lbrack {{Equation}\mspace{14mu} 4} \rbrack\end{matrix}$

A pseudo-random sequence c(i) is defined by a gold sequence oflength-31, and a pseudo-random sequence generator is initialized at thestart of each subframe as in the following Equation 5.c _(init)=(└n _(s)/2┘+1)·(2n _(ID) ^((n) ^(SCID) ⁾+1)·2¹⁶ +n_(SCID)  [Equation 5]

n_(ID) ^((i)) quantity (i=0,1) is given below.

-   -   n_(ID) ^((i))=N_(ID) ^((cell)), if no value for n_(ID)        ^((PCRS,i)) is provided by higher layers.    -   n_(ID) ^((i))=n_(ID) ^((PCRS,i)), if any value for n_(ID)        ^((PCRS,i)) is provided by higher layers.

A value of n_(SCID) is zero unless otherwise specified. For a xPUSCHtransmission, SCID is given by a DCI format related to the xPUSCHtransmission.

Mapping to Resource Elements

For antenna ports p∈{40,41,42,43}, in a physical resource block with afrequency domain index n_(pRB) assigned for the corresponding xPUSCHtransmission, a part of the reference signal sequence r(m) is mapped tocomplex-value modification symbols a_(k,l) ^((p)) for correspondingxPUSCH symbols in a subframe according to a_(k,l) ^((p))=r(k″).

For a start physical resource block index n_(PRB) ^(xPUSCH) of xPUSCHphysical resource allocation and the number N_(PRB) ^(xPUSCH) of xPUSCHphysical resource blocks, resource elements (k,l′) in one subframe aregiven by the following Equation 6.

$\begin{matrix}{{k = {{N_{sc}^{RB} \cdot ( {n_{PRB}^{xPUSCH} + {k^{''} \cdot 4}} )} + k^{\prime}}}{k^{\prime} = \{ {{\begin{matrix}16 & {p \in \{ {40,41} \}} \\31 & {p \in \{ {42,43} \}}\end{matrix}k^{''}} = {{\lfloor {m^{\prime}/4} \rfloor l^{\prime}} = \{ {{{\begin{matrix}{\{ {l^{\prime}❘{l^{\prime} \in {\{ {3,\ldots\mspace{14mu},l_{last}^{\prime\;{xPUSCH}}} \}{and}\mspace{14mu} l^{\prime}\mspace{14mu}{is}\mspace{14mu}{an}\mspace{14mu}{odd}\mspace{14mu}{number}}}} \},} & {p \in \{ {{40 + m^{''}},{42 + m^{''}}} \}} \\{\{ {l^{\prime}❘{l^{\prime} \in {\{ {3,\ldots\mspace{14mu},l_{last}^{\prime\;{xPUSCH}}} \}{and}\mspace{14mu} l^{\prime}\mspace{14mu}{is}\mspace{14mu}{an}\mspace{14mu}{even}\mspace{14mu}{number}}}} \},} & {p \in \{ {{41 - m^{''}},{43 - m^{''}}} \}}\end{matrix}m^{\prime}} = 0},1,2,\ldots\mspace{14mu},{{N_{PRB}^{xPUSCH} - {1m^{''}}} = {\lfloor {m^{\prime}/4} \rfloor{mod}\; 2}}} }} }} & \lbrack {{Equation}\mspace{14mu} 6} \rbrack\end{matrix}$

In Equation 6, m′=0, 1, 2, . . . , N_(PRB) ^(xPUSCH), l′ denotes asymbol index in one subframe, and l′_(last) ^(xPUSCH) denotes a lastsymbol index of xPUSCH in a given subframe.

Resource elements (k, l′) used for transmission of a UE-specific PCRSfrom one UE on any antenna port in a set S are not used for transmissionof xPUSCH on any antenna port in the same subframe.

Here, S is {40}, {41}, {42}.

Carrier Frequency Offset (CFO) Effect

A baseband signal transmitted from a transmitter (e.g., base station)transitions to a passband by a carrier frequency generated in anoscillator, and a signal transmitted through the carrier frequency isconverted to the baseband signal by the same carrier frequency at areceiver (e.g., UE).

In this case, a signal received by the receiver may include a distortionrelated to the carrier.

An example of the distortion may include a distortion phenomenon causedby a difference between a carrier frequency of the transmitter and acarrier frequency of the receiver.

This carrier frequency offset occurs because the oscillators used in thetransmitter and the receiver are not the same or Doppler frequency shiftoccurs depending on a movement of the UE.

A Doppler frequency is proportional to a moving speed of the UE and thecarrier frequency and is defined by the following Equation 7.

$\begin{matrix}{f_{d} = \frac{v \cdot f_{c}}{c}} & \lbrack {{Equation}\mspace{14mu} 7} \rbrack\end{matrix}$

In Equation 7, f_(c), f_(d), v, c denote the carrier frequency, theDoppler frequency, the moving speed of the UE, and a speed of light,respectively.

Further, a normalized carrier frequency offset (ε) is defined by thefollowing Equation 8.

$\begin{matrix}{ɛ = \frac{f_{offset}}{\Delta\; f}} & \lbrack {{Equation}\mspace{14mu} 8} \rbrack\end{matrix}$

In Equation 8, f_(offset), Δf, ε denote a carrier frequency offset, asubcarrier spacing, and a carrier frequency offset normalized at asubcarrier spacing, respectively.

When the carrier frequency offset is present, a received signal of thetime domain is a result of multiplying a transmitted signal by a phaserotation, and a received signal of the frequency domain is a result ofshifting a transmitted signal in the frequency domain.

In this case, the received signal is affected by all of othersubcarrier(s), and inter-carrier-interference (ICI) occurs.

That is, when a fractional carrier frequency offset occurs, the receivedsignal of the frequency domain is represented by the following Equation9.

Equation 9 indicates a received signal with the CFO in the frequencydomain.

$\begin{matrix}{{Y_{l}\lbrack k\rbrack} = {{e^{j\;\pi\;{{ɛ{({N - 1})}}/N}}\{ \frac{\sin\;\pi\; ɛ}{N\;{\sin( {\pi\;{ɛ/N}} )}} \}{H_{l}\lbrack k\rbrack}{X_{l}\lbrack k\rbrack}} + {I_{l}\lbrack k\rbrack} + {Z\lbrack k\rbrack}}} & \lbrack {{Equation}\mspace{14mu} 9} \rbrack\end{matrix}$

In Equation 9, k, l, N, Y[·], X[·], H[·], I[·], Z[·] denote a subcarrierindex, a symbol index, a FFT size, a received signal, a transmittedsignal, a frequency response, ICI resulting from the CFO, a white noise,respectively.

As defined by the above Equation 9, if the carrier frequency offset ispresent, an amplitude and a phase of a k-th subcarrier may be distorted,and interference due to adjacent subcarriers may occur.

If the carrier frequency offset is present, the interference due toadjacent subcarriers may be given by the following Equation 10.

Equation 10 indicates the ICI caused by the CFO.

$\begin{matrix}{{I_{l}\lbrack k\rbrack} = {e^{j\;\pi\;{{ɛ{({N - 1})}}/N}}{\sum\limits_{\underset{m \neq k}{m = 0}}^{N - 1}{{H\lbrack m\rbrack}{X_{l}\lbrack m\rbrack}{\quad{\{ \frac{\sin\;\pi\; ɛ}{N\;{\sin( {{\pi( {m - k + ɛ} )}/N} )}} \} e^{{- j}\;{{\pi{({m - k})}}/N}}}}}}}} & \lbrack {{Equation}\mspace{14mu} 10} \rbrack\end{matrix}$

Phase Noise Effect

As described above, a baseband signal transmitted from the transmittertransitions to a passband by a carrier frequency generated in anoscillator, and a signal transmitted through the carrier frequency isconverted to the baseband signal by the same carrier frequency at thereceiver.

A signal received by the receiver may include a distortion related tothe carrier.

An example of the distortion may include a phase noise generated due tounstable characteristics of the oscillator used in the transmitter andthe receiver.

The phase noise refers to that a frequency varies with time around acarrier frequency.

The phase noise is modeled as a Wiener process as a random process withan average of zero and affects an OFDM system.

As illustrated in FIG. 6 below, the phase noise tends to increase itsinfluence as the frequency of the carrier increases.

The phase noise tends to determine its characteristics depending on thesame power spectral density as the oscillator.

FIG. 6 illustrates an example of a power spectral density of anoscillator.

A distortion phenomenon of a signal resulting from the phase noise asdescribed above is represented as a common phase error (CPE) and aninter-carrier interference (ICI) in an OFDM system.

The following Equation 11 indicates an influence of the phase noise on areceived signal of the OFDM system. That is, the following Equation 11indicates a received signal with the phase noise in the frequencydomain.

$\begin{matrix}{{{Y_{l}(k)} = {{{X_{l}(k)}{H_{l}(k)}{I_{l}(0)}} + {{ICI}_{l}(k)} + {Z_{l}(k)}}}{where}{{{ICI}_{l}(k)} = {\sum\limits_{{m = 0},{m \neq k}}^{N - 1}{{X_{l}(m)}{H_{l}(m)}{I_{l}( {m - k} )}}}}{and}{{I_{l}(p)} = {\frac{1}{N}{\sum\limits_{n = 0}^{N - 1}e^{j{\lbrack{\frac{2\;\pi\;{pn}}{N} + {\phi_{l}{(n)}}}\rbrack}}}}}} & \lbrack {{Equation}\mspace{14mu} 11} \rbrack\end{matrix}$

In the above Equation 11, k, l, N, Y(·), X(·), H(·), I(0), ICI(·), Z(·),ϕ(·) denotes a subcarrier index, a symbol index, a FFT size, a receivedsignal, a transmitted signal, a frequency response, a common phase errorresulting from the phase noise, inter-carrier interference resultingfrom the phase noise, a white noise, phase rotation resulting from thephase noise, respectively.

Doppler in mmWAVE Band

An ultrahigh frequency wireless communication system is configured suchthat a center frequency operates at several GHz to several tens of GHz,unlike an existing wireless communication system.

Ultrahigh frequency characteristics of the center frequency make worse aDoppler effect appearing according to a movement of the UE or an impactof a carrier frequency offset (CFO) generated by an oscillator errorbetween the UE and the base station.

In this instance, the Doppler effect has a characteristic of linearlyincreasing in response to the center frequency. The CFO generated by theoscillator error between the UE and the base station is indicated in appm (=10⁻⁶) and also has a characteristic of linearly increasing inresponse to the center frequency.

In an existing cellular network system, in order to solve a problem ofthe CFO described above, the base station transmits a synchronizationchannel, a pilot signal, or a reference symbol to the UE, and the UEestimates or compensates the CFO using them.

Accordingly, in the ultrahigh frequency wireless communication system, asynchronization channel has to be transmitted in a different way, inorder to estimate (or compensate) the CFO of which an offset value isgreater than an offset value of the existing wireless communicationsystem.

In an existing LTE/LTE-A system, an error value of oscillators betweenthe use of the UE and the base station is defined by requirements asfollows.

UE side frequency error (TS. 36.101)

The UE modulated carrier frequency needs to be accurate to within ±0.1PPM observed over a period of one time slot (0.5 ms) compared to acarrier frequency received from the E-UTRA Node B.

eNB side frequency error (TS. 36.104)

The frequency error is the measure of a difference between an actual BStransmit frequency and an assigned frequency.

The following Table 4 shows an example of oscillator accuracy accordingto a class of the base station.

TABLE 4 BS class Accuracy Wide Area BS ±0.05 ppm Local Area BS  ±0.1 ppmHome BS ±0.25 ppm

Accordingly, a maximum difference of oscillators between the basestation and the UE is ±0.1 ppm. If an error has occurred in onedirection, it may have a maximum offset value of 0.2 ppm.

A mathematical equation for converting the value of ppm into a unit ofHz suitable for each center frequency may be given by centerfrequency*frequency offset (ppm).

In the OFDM system, an impact of a CFO value may vary depending on asubcarrier spacing.

In general, the OFDM system having a large subcarrier spacing is lessaffected by even a large CFO value.

Therefore, an actual CFO value (absolute value) needs to be expressed asa relative value that affects the OFDM system, and may be referred to asnormalized CFO and may be expressed as carrier frequency (Hz)/subcarrierspacing in a mathematical equation.

The following Table 5 shows an example of CFO values depending on eachcenter frequency and the offset value.

TABLE 5 Center frequency (sub carrier Oscillator Offset spacing) ±0.05ppm ±0.1 ppm ±10 ppm ±20 ppm  2 GHz  ±100 Hz ±200 Hz  ±20 kHz   ±40 kHz(15 kHz) (±0.0067) (±0.0133) (±1.3) (±2.7) 30 GHz  ±1.5 kHz  ±3 kHz ±300kHz  ±600 kHz (104.25 kHz) (±0.014) (±0.029) (±2.9) (±5.8) 60 GHz   ±3kHz  ±6 kHz ±600 kHz  ±1.2 MHz (104.25 kHz) (±0.029) (±0.058) (±5.8)(±11.5)

Table 5 indicates CFO value and normalized CFO for each center frequencyand an error value of an oscillator.

It was assumed that a subcarrier spacing used in LTE Rel-8/9/10 was 15kHz when a center frequency was 2 GHz. It was assumed that subcarrierspacings at the center frequencies of 30 GHz and 60 GHz were 104.25 kHzso that performance degradation was avoided considering the Dopplereffect for each center frequency.

However, Table 5 is merely an example, and it will be apparent thatother subcarrier spacings may be used for each center frequency.

A Doppler spread phenomenon is greatly affected in a situation where theUE moves at high speed or moves at low speed in a high frequency band.

Doppler spread causes spread in a frequency domain, and as a resultgenerates distortion of a signal.

The Doppler spread may be represented by the following Equation 12.f _(doppler)=(v/λ)cos θ  [Equation 12]

In Equation 12, v denotes a moving speed of the UE, and λ denotes awavelength of a center frequency of a radio wave the base station or theUE transmits.

Further, θ denotes an angle between the received radio wave and a movingdirection of the UE.

Hereinafter, description will be given on the assumption that θ is ‘0’.

In this case, a coherence time T_(c) has a relationship of the followingEquation 13.

$\begin{matrix}{T_{c} \approx \frac{1}{f_{doppler}}} & \lbrack {{Equation}\mspace{14mu} 13} \rbrack\end{matrix}$

If the coherence time is defined as a time spacing in which acorrelation value of a channel response in a time domain is 50% or more,the coherence time T_(c) may be represented by the following Equation14.

$\begin{matrix}{T_{c} \approx \frac{9}{16\;\pi\; f_{doppler}}} & \lbrack {{Equation}\mspace{14mu} 14} \rbrack\end{matrix}$

The wireless communication system mainly uses a relationship between thecoherence time and the Doppler spread using a geometric mean of theabove two Equations as in the following Equation 15.

$\begin{matrix}{T_{c} = {\sqrt{\frac{9}{16\;\pi\; f_{doppler}}} = \frac{0.423}{f_{doppler}}}} & \lbrack {{Equation}\mspace{14mu} 15} \rbrack\end{matrix}$

Such a Doppler power spectrum density (hereinafter referred to asDoppler spectrum) may have various shapes.

Generally, if signals received by the UE are received at the same powerin all directions in a rich scattering environment such as downtownarea, the Doppler spectrum is indicated in the U-shape as shown in FIG.7.

FIG. 7 illustrates an example of a U-shaped Doppler spectrum.

A U-shaped Doppler spectrum when a center frequency is fc and a maximumDoppler spread value is fd may be given by FIG. 7.

In the ultrahigh frequency wireless communication system, since thecenter frequency is located at a very high band, there is an advantagethat a size of an antenna is small and several antennas can be installedin a small space.

The advantage enables pin-point beamforming (may be referred to aspencil beamforming, narrow beamforming, or sharp beamforming) usingseveral tens to several hundreds of antennas.

The narrow beamforming means that a received signal is not received in aconstant direction and is received only at a certain angle.

FIG. 8 illustrates a concept when an existing Doppler spectrum performsnarrow beamforming using multiple U-shaped antennas of a signal receivedin a constant direction.

In other words, FIG. 8 illustrates an example of reduced angular spread.

As described above, due to the reduced angular spread when the narrowbeamforming has been performed, the Doppler spectrum does not have theU-shape and has Doppler spread only at a certain band.

FIG. 9 illustrates a Doppler spectrum when narrow beamforming has beenperformed or when a signal received by a receiver (or UE) is notincident in a constant direction and has been incident only at a narrowangle.

FIG. 9 illustrates an example of a Doppler spectrum in narrowbeamforming.

Beamforming/Multi-Level Repetition Based Synchronization Signal

The UE performs timing and frequency synchronization with acorresponding base station using a (downlink) synchronization signaltransmitted by the base station.

At this time, the base station transmits a downlink synchronizationsignal with as wide beam width as possible, so that all of UEs within aspecific cell can use the synchronization signal.

If the base station transmits a (downlink) synchronization signal usinga high frequency (e.g., mmWave) band, the synchronization signalexperiences larger path attenuation than a synchronization signal usinga low frequency band.

Namely, in case of a system transmitting a downlink synchronizationsignal using a high frequency band, a supportable cell radius of thesystem is greatly reduced compared to an existing cellular system (e.g.,LTE) using a relatively low frequency band (under 6 GHz).

One method for solving the reduction of the cell radius is to transmit a(downlink) synchronization signal using a beamforming scheme.

In this case, a cell radius increases, but a beam width decreases.

The following Equation 16 indicates change in a received SINR (Signal toInterference Noise Ratio) depending on a beam width.W→M ⁻² WSINR→M ²SINR  [Equation 16]

The above Equation 16 shows that if a beam width is reduced by M⁻² timesan existing beam width, the received SINR is improved by M² times.

Another method is to repeatedly transmit the same downlinksynchronization signal several times.

In this case, while additional resource allocation is necessary on atime axis, a cell radius can be increased while maintaining a beam widthas it is.

One base station schedules a frequency resource and a time resourceshared by UEs present in a specific area and allocates them to each UE.

Hereinafter, the specific area is defined as ‘sector’.

FIG. 10 illustrates an example of a downlink synchronization signalservice area of a base station.

Namely, FIG. 10 illustrates a specific area, i.e., a sector.

Referring to FIG. 10, A1, A2, A3, and A4 denote sectors having widths of0′-15′, 15′-30′, 30′-45′ and 45′-60′ in a radius of 0 to 200 m,respectively.

Further, B1, B2, B3, and B4 denote sectors having widths of 0′-15′,15′-30′, 30′-45′ and 45′-60′ in a radius of 200 m to 500 m,respectively.

Based on this, Sector I and Sector II are defined as follows.

Sector I: A1, A2, A3, A4

Sector II: A1, A2, A3, A4, B1, B2, B3, B4

It is assumed that a service area of an existing downlinksynchronization signal is Sector I.

Further, in order to service the Sector II, assume that a power of thesynchronization signal has to additionally increase to 6 dB or more.

First, if an additional gain of 6 dB is provided using a beamformingscheme, a service radius can be extended from A1 to B1.

However, because a beam width is reduced, A2, A3, and A4 cannot beserviced simultaneously.

Thus, A2-B2, A3-B3, and A4-A4 have to be serviced next.

Namely, in order to service the Sector II, the downlink synchronizationsignal has to be transmitted while changing a beam direction four times.

On the other hand, if the repetitive transmission of the synchronizationsignal is used, the whole Sector II can be serviced simultaneously.However, the same four synchronization signals need to be transmitted onthe time axis.

As a result, a resource required to service all the above sectors isidentical for the two methods.

Because a beam width is narrow in the former method, the UE may miss asynchronization signal when the UE moves fast or is located at eachsector boundary.

However, if the UE can identify an ID of a beam transmitted to eachsector, the UE can grasp which sector the UE has been located in throughthe synchronization signal.

On the other hand, because a beam having a wide beam width is used inthe latter method, it is less probable that the UE misses asynchronization signal. Instead, the UE cannot grasp which sector the UEhas been located in.

mmWave Frame Structure

FIG. 11 illustrates an example of an mmWave frame structure.

Referring to FIG. 11, one frame is composed of Q subframes, and onesubframe is composed of P slots.

Further, the slot is composed of T OFDM symbols.

In this instance, unlike other subframes, a first subframe uses 0th slotfor the usage of synchronization.

The S slot is composed of A OFDM symbols for timing and frequencysynchronization, B OFDM symbols for beam scanning, and C OFDM symbolsfor informing the UE of system information.

Remaining D OFDM symbols are used for data transmission to each UE.

Existing Timing Synchronization Algorithm

In FIG. 11, assume that the base station repeatedly transmits the samesignal A times.

Based on the synchronization signal repeatedly transmitted by the basestation, the UE performs timing synchronization using the following twoalgorithms.

The following Equation 17 indicates an example of a timingsynchronization algorithm based on a correlation of received signals.

$\begin{matrix}{{\hat{n} = {\underset{\overset{\sim}{n}}{\arg\;\max}\frac{{\sum\limits_{i = 0}^{A - 2}{y_{\overset{\sim}{n},i}^{H}y_{\overset{\sim}{n},{i + 1}}}}}{\sum\limits_{i = 0}^{A - 2}{{y_{\overset{\sim}{n},i}^{H}y_{\overset{\sim}{n},{i + 1}}}}}}}{where}y_{\overset{\sim}{n},i} = {r\lbrack {{\overset{\sim}{n} + {i( {N + N_{g}} )}}:{\overset{\sim}{n} + {i( {N + N_{g}} )} + N - 1}} \rbrack}} & \lbrack {{Equation}\mspace{14mu} 17} \rbrack\end{matrix}$

In the above Equation 17, N, N_(g), i denote a length of an OFDM symbol,a length of Cyclic Prefix, and an index of the OFDM symbol,respectively.

Further, r means a received signal vector.

Here, y_(ñ,i)=r[ñ+i(N+N_(g)):ñ+i(N+N_(g))+N−1] is a vector defined withelements from (

i(N+N_(g)))-th element to (

i(N+N_(g))+N−1)-th element of the received signal vector r.

The timing synchronization algorithm of Equation 17 operates on theassumption that two temporally adjacent OFDM received signals are equalto each other.

Since the algorithm can use a sliding window scheme, it can beimplemented with low complexity and has a property robust to a frequencyoffset.

The following algorithm performs timing synchronization using acorrelation between a received signal and a signal transmitted by thebase station.

The following Equation 18 indicates an example of a timingsynchronization algorithm based on a correlation between a receivedsignal and a transmitted signal.

$\begin{matrix}{\hat{n} = {\underset{n\%}{\arg\;\max}\frac{{{\sum\limits_{i = 0}^{A - 1}{y_{{n\%},i}^{H}s}}}^{2}}{\sum\limits_{i = 0}^{A - 1}{{y_{{n\%},i}}^{2}{\sum\limits_{i = 0}^{A - 1}{s}^{2}}}}}} & \lbrack {{Equation}\mspace{14mu} 18} \rbrack\end{matrix}$

In the above Equation 18, s means a signal transmitted by the basestation and is a signal vector promised in advance between the UE andthe base station.

The scheme indicated in Equation 18 has a performance better than thescheme indicated in Equation 17.

However, since the scheme of Equation 18 cannot be implemented by thesliding window scheme, it requires high complexity.

In addition, the scheme of Equation 18 has a property vulnerable to afrequency offset.

Beam Scanning

Beam scanning indicates an operation of a transmitter or a receiver thatfinds a direction of a beam maximizing a received SINR of the receiver.

For example, the base station determines a direction of a beam throughthe beam scanning before transmitting data to the UE.

The description related to the beam scanning is briefly given below.

FIG. 10 shows that one sector serviced by one base station is dividedinto a total of 8 areas.

Here, it is assumed that an area of each beam transmitted by the basestation is (A1-B1)/(A2-B2)/(A3-B3)/(A4-B4).

Further, it is assumed that the UE can identify the beams transmitted bythe base station.

Based on this, the beam scanning can be specified as follows.

The base station transmits beams to (A1-B1)/(A2-B2)/(A3-B3)/(A4-B4) insequence.

(1) The UE finds a best beam among the beams in terms of a receivedSINR.

(2) The UE feeds back the found beam to the base station.

(3) The base station transmits data using a beam with a direction of thefeedback.

(4) Consequently, the UE can receive data from a beam having a maximizedreceived SINR.

Zadoff-Chu (ZC) Sequence

Zadoff-Chu sequence is called Chu sequence or ZC sequence.

Hereinafter, Zadoff-Chu sequence is commonly called ‘ZC sequence’.

The ZC sequence is defined by the following Equation 19.

$\begin{matrix}{{x_{r}\lbrack n\rbrack} = e^{\frac{j\;\pi\;{{rn}{({n + 1})}}}{N}}} & \lbrack {{Equation}\mspace{14mu} 19} \rbrack\end{matrix}$

In the above Equation 19, N denotes a sequence length, r denotes a rootvalue, and x_(r) [n] denotes an n-th elementof the ZC sequence.

The ZC sequence has the following three important properties.

(1) All elements of the ZC sequence are the same in size (ConstantAmplitude).

A DFT result of the ZC sequence is also identical for the sizes of allelements.

(2) A correlation between the ZC sequence and a cyclic shift version ofthe ZC sequence is given by the following Equation 20.

$\begin{matrix}{{( x_{r}^{(i)} )^{H}x_{r}^{(j)}} = \{ \begin{matrix}N & {{{for}\mspace{14mu} i} = j} \\0 & {elsewhere}\end{matrix} } & \lbrack {{Equation}\mspace{14mu} 20} \rbrack\end{matrix}$

In Equation 20, x_(r) ^((i)) is defined as a sequence obtained by cyclicshifting x_(r) by i.

The above Equation 20 indicates that auto-correlation of the ZC sequenceis zero except when i=j. (Zero Auto-Correlation)

The ZC sequence is also called CAZAC sequence because it has ConstantAmplitude Zero Auto-Correlation properties.

(3) A correlation between ZC sequences having root values, which arecoprime to a length N, is given by the following Equation 21.

$\begin{matrix}{{x_{r_{1}}^{H}x_{r_{2}}} = \{ \begin{matrix}N & {{{for}\mspace{14mu} r_{1}} = r_{2}} \\\frac{1}{\sqrt{N}} & {elsewhere}\end{matrix} } & \lbrack {{Equation}\mspace{14mu} 21} \rbrack\end{matrix}$

In Equation 21, r₁,r₂ are coprime to N.

For example, when N=111, 2≤r₁, r₂≤110 always satisfies the aboveEquation 21.

Unlike the auto-correlation of Equation 20, a mutual correlation of ZCsequence does not become zero completely.

Hadamard Matrix

Hadamard matrix is defined by the following Equation 22.

$\begin{matrix}{{H_{2^{k}} = {\begin{bmatrix}H_{2^{k - 1}} & H_{2^{k - 1}} \\H_{2^{k - 1}} & {- H_{2^{k - 1}}}\end{bmatrix} = {H_{2} \otimes H_{2^{k - 1}}}}}{{{where}\mspace{14mu} H_{1}} = \lbrack 1\rbrack}{H_{2} = \begin{bmatrix}1 & 1 \\1 & {- 1}\end{bmatrix}}} & \lbrack {{Equation}\mspace{14mu} 22} \rbrack\end{matrix}$

In Equation 22, 2^(k) denotes a size of a matrix.

Hadamard matrix always satisfies H_(n)H_(n) ^(T)=nI_(n) regardless ofsize n.

Namely, Hadamard matrix is a Unitary matrix, and all columns (rows) areorthogonal to each other.

For example, when n=4, Hadamard matrix is defined by the followingEquation 23.

$\begin{matrix}{H_{4} = \begin{bmatrix}1 & 1 & 1 & 1 \\1 & {- 1} & 1 & {- 1} \\1 & 1 & {- 1} & {- 1} \\1 & {- 1} & {- 1} & 1\end{bmatrix}} & \lbrack {{Equation}\mspace{14mu} 23} \rbrack\end{matrix}$

In the matrix of the above Equation 23, it can be confirmed that columnsare orthogonal to each other.

Orthogonal Variable Spreading Factor (OVSF) Code

An OVSF code is based on Hadamard matrix and is generated according tothe following rule.

When the OVSF code branches to the right (lower branch), a first coderepeats an upper code (mother code) as it is twice, and a second coderepeats the upper code as it is once, inverts the upper code, and thenrepeats the inverted upper code once.

FIG. 12 illustrates an example of an OVSF code tree structure.

That is, the OVSF code has the following properties.

(1) The orthogonality is secured except a relationship between a mothercode and a child code that are immediately adjacent on a code tree.

In FIG. 12, [1−1 1−1] is orthogonal to [1 1], [1 1 1 1], and [1 1−1 −1].

(2) A length of a code is the same as the number of available codes.

FIG. 12 illustrates that a length of a code is the same as the totalnumber of branches to which a corresponding code belongs.

Random Access Channel (RACH)

Transmit Power Control of RACH Signal

In case of LTE system, when RACH signals transmitted by a plurality ofUEs arrive at the base station, the RACH signals of the UEs received bythe base station need to have the same power.

To this end, the base station defines a parameter‘preambleInitialReceivedTargetPower’ and broadcasts the parameter to allUEs within a corresponding cell through SIB2.

The UE calculates a path loss using a reference signal and determines atransmit power of the RACH signal using the calculated path loss and theparameter ‘preambleInitialReceivedTargetPower’ as in the followingEquation 24.P_PRACH_Initial=min{P_CMAX,preambleInitialReceivedTargetPower+PL}  [Equation24]

In Equation 24, P_PRACH_Initial, P_CMAX, and PL denote a transmit powerof the RACH signal, a maximum transmit power of the UE, and a path loss,respectively.

For example, a maximum transmittable power of the UE is assumed as 23dBm.

An RACH receive power of the base station is assumed as −104 dBm.

It is assumed that the UE has been located as shown in FIG. 13.

Namely, FIG. 13 illustrates an example of distribution of UEs.

First, the UE calculates a path loss using a received synchronizationsignal and a beam scanning signal and then determines a transmit powerbased on the calculation.

The following Table 6 shows a path loss and a transmit power of each UE.

TABLE 6 Necessary Additional preambleInitial Path transmit Transmitnecessary UE ReceivedTargetPower loss power power power K1 −104 dBm  60dB −44 dBm −44 dBm 0 dBm K2 −104 dBm 110 dB   6 dBm   6 dBm 0 dBm K3−104 dBm 130 dB  26 dBm  23 dBm 3 dBm

In Table 6, in case of a UE K1, although a path loss is very small, theUE K1 transmits an RACH signal with very small power (−44 dBm) in orderto match an RACH receive power.

In case of a UE K2, although a path loss is large, the UE K2 maytransmit an RACH signal with a necessary transmit power of 6 dBm.

However, in case of a UE K3, since a path loss is very large, anecessary transmit power exceeds P_CMA=23 dBm.

In this case, because the UE has to perform a transmission with 23 dBm,an RACH access success rate of the corresponding UE is reduced by 3 dB.

Phase Noise

A jitter on a time axis is defined as a phase noise on a frequency axis.

The phase noise changes with a time dependent correlation, and this isrepresented as a common phase error (CPE).

Hereinafter, various embodiments of a PCRS for compensating a phasenoise and a Doppler impact proposed by this specification are describedin detail.

In each embodiment, signaling related to a DM-RS is as follows.

Namely, the base station transmits transmission information of DL-SCHfor the UE to the UE via DCI or RRC signaling.

Here, the transmission information of DL-SCH may include a precodingscheme, a number of transmission ranks, an MCS level, etc.

The UE checks a transmission scheme of DL-SCH based on information ofthe DCI or RRC signaling received from the base station.

The UE can implicitly check a location of a DM-RS for demodulation of aDL-SCH symbol based on the transmission scheme of DL-SCH.

This is because a location of a DM-RS for each transmission scheme ispromised in advance between a transmitter (e.g., base station) and areceiver (e.g., UE).

A PCRS proposed by each of the following embodiments may be definedbased on the DM-RS.

First Embodiment

A first embodiment provides a method of reusing as it is a demodulationreference signal (DM-RS) located on the same frequency axis as areference signal used for compensating a phase noise and a Dopplerimpact.

In this specification, a reference signal used for compensating a phasenoise and a Doppler impact is called or represented as ‘Phase noiseCompensation Reference Signal (PCRS)’.

FIG. 14 illustrates an example of a location on time and frequency axesof a PCRS proposed by this specification.

Namely, FIG. 14 illustrates a method of reusing as it is a DM-RS locatedon the same frequency axis as described above when defining a PCRS.

In other words, FIG. 14 illustrates an example of a method of utilizinga DM-RS located on the same frequency axis as a PCRS.

Referring to FIG. 14, a sequence of a PCRS can reuse as it is a sequenceof a DM-RS located on the same frequency axis as a frequency axis onwhich the PCRS is defined.

In FIG. 14, Type I indicates a structure in which a PCRS is nottransmitted on all symbols and is transmitted on a time axis atintervals of one symbol, and Type II indicates a structure in which aPCRS is transmitted over all symbols on a time axis.

It can be seen that the PCRS uses different frequency axis resourcesaccording to an antenna port.

Further, it can be seen that the PCRS equally uses a DM-RS used insubcarrier indices ‘5’ and ‘6’ of a third symbol (symbol #2) and istransmitted at intervals of one symbol or over all the symbols fromafter a symbol, to which the DM-RS is transmitted.

Further, it can be seen that a PCRS transmitted through an antenna port‘0’ is transmitted on a frequency axis corresponding to the subcarrierindex ‘5’, and a PCRS transmitted through an antenna port ‘1’ istransmitted on a frequency axis corresponding to the subcarrier index‘6’.

Second Embodiment

Next, a second embodiment provides a method for transmitting a PCRS whena DM-RS is not located on the same frequency axis as a frequency axis onwhich the PCRS is transmitted.

If a DM-RS is not present on the same frequency axis as a frequency axison which a PCRS is transmitted, the PCRS reuses as it is a DM-RS locatedon a frequency axis closest to the frequency axis on which the PCRS istransmitted.

The DM-RS may be defined, or located, or transmitted at certainintervals on the frequency axis in consideration of a coherencebandwidth, a reference signal overhead, etc.

In this case, in the PCRS, directly mapped DM-RSs may not be present onthe frequency axis.

FIG. 15 illustrates another example of a location on time and frequencyaxes of a PCRS proposed by this specification.

Accordingly, if a DM-RS is not present on the same frequency axis as afrequency axis on which a PCRS is transmitted, the PCRS reuses as it isa DM-RS closest to the frequency axis.

It can be seen from FIG. 15 that a PCRS corresponding to an antenna port‘0’ reuses as it is a DM-RS sequence located on #4 frequency axis (orsubcarrier index ‘4’), and a PCRS corresponding to an antenna port ‘1’reuses as it is a DM-RS sequence located on #5 frequency axis.

In FIG. 15, Type I indicates a structure in which a PCRS is nottransmitted on all symbols and is transmitted on a time axis atintervals of one symbol, and Type II indicates a structure in which aPCRS is transmitted over all symbols on a time axis.

Here, it is assumed that the PCRS is transmitted after the DM-RStransmission.

It can be seen that the PCRS uses different frequency axis resourcesaccording to an antenna port.

Further, it can be seen that the PCRS equally uses a DM-RS used insubcarrier indices ‘5’ and ‘6’ of a third symbol (symbol #2) and istransmitted at intervals of one symbol or over all the symbols fromafter a symbol, to which the DM-RS is transmitted.

Third Embodiment

Next, a third embodiment provides a method of defining and using allPCRSs, that are assigned to all resources and compensate for a phasenoise and a Doppler impact, as the same specific complex value.

As described above, when a common phase error (CPE) or a carrierfrequency offset (CFO) is estimated using the PCRSs, there is anadvantage that the UE can omit a descrambling process if data ofcontiguous resource elements on a time axis is the same.

Accordingly, in order to utilize the above advantage, the thirdembodiment provides a method of defining all PCRSs assigned to allresources as the same specific complex value.

FIG. 16 illustrates another example of a location on time and frequencyaxes of a PCRS proposed by this specification.

Referring to FIG. 16, S₀ and S₁ mean the same complex value defined in aPCRS of an antenna port ‘0’ and the same complex value defined in a PCRSof an antenna port ‘1’, respectively.

Namely, a PCRS transmitted on the antenna port ‘0’ equally uses acomplex value used in a symbol #2 and a subcarrier index #5 in a symbolto which a subsequent PCRS is transmitted, and a PCRS transmitted on theantenna port ‘1’ equally uses a complex value used in the symbol #2 anda subcarrier index #6 in a symbol to which a subsequent PCRS istransmitted.

In FIG. 16, Type I indicates a structure in which a PCRS is nottransmitted on all symbols and is transmitted on a time axis atintervals of one symbol, and Type II indicates a structure in which aPCRS is transmitted over all symbols on a time axis.

It can be seen that the PCRS uses different frequency axis resources(subcarrier indices #5 and #6) according to an antenna port.

Further, it can be seen that the PCRS equally uses a DM-RS used insubcarrier indices ‘5’ and ‘6’ of a third symbol (symbol #2) and istransmitted at intervals of one symbol or over all the symbols fromafter a symbol, to which the DM-RS is transmitted.

Further, it can be seen that a PCRS transmitted on the antenna port ‘0’is transmitted on a frequency axis corresponding to the subcarrier index‘5’, and a PCRS transmitted on the antenna port ‘1’ is transmitted on afrequency axis corresponding to the subcarrier index ‘6’.

Fourth Embodiment

Next, a fourth embodiment provides a method of defining PCRSs forseveral resource elements of frequency axes on the same time axis usingdifferent sequences or different specific values, copying the same valueof the same frequency axis onto different time axes, and reusing a PCRS.

When a common phase error (CPE) or a carrier frequency offset (CFO) isestimated using a PCRS, there is an advantage that the UE can omit adescrambling process if data of contiguous resource elements on a timeaxis is the same.

Further, there is an advantage that a performance of a reference signalcan be improved by defining each of PCRSs on several frequency axes.

As a method for utilizing the advantages, the fourth embodiment providesa method of defining several resource elements of frequency axes on thesame time axis using a gold sequence, copying the same gold sequenceonto a different time axis, and reusing the PCRS.

FIG. 17 illustrates another example of a location on time and frequencyaxes of a PCRS proposed by this specification.

Namely, FIG. 17 illustrates an example of a PCRS defined using aspecific complex value on multiple frequency axes.

Referring FIG. 17, S₀, S₁, S₂, and S₃ mean the first same complex valuedefined in a PCRS of an antenna port ‘0’, the second same complex valuedefined in the PCRS of the antenna port ‘0’, the first same complexvalue defined in a PCRS of an antenna port ‘1’, and the second samecomplex value defined in the PCRS of the antenna port ‘1’, respectively.

In this instance, S₀, S₁, S₂, and S₃ may be defined as values promisedin advance between a transmitter and a receiver.

Alternatively, S₀, S₁, S₂, and S₃ may be sequences generated by applyingan input of at least one of a Cell ID, a symbol index, or a subcarrierlocation to a specific sequence.

Further, S₀, S₁, S₂, and S₃ may have the same value.

Namely, S₀=S₁ and S₂=S₃.

A relationship of S₀, S₁, S₂, and S₃ may be defined by downlink controlinformation (DCI) or radio resource control (RRC) signaling or may bepromised in advance between the transmitter and the receiver.

In addition, in the above first to fourth embodiments, the PCRS portsare not limited to two.

Namely, the above-described methods may be equally applied to one PCRSport or three or more PCRS ports.

FIG. 18 is a flow chart illustrating an example of a method fortransmitting and receiving a PCRS proposed by this specification.

First, a UE receives, from a base station, control information relatedto transmission of downlink data in S1810.

The control information may include at least one of a precoding schemerelated to the downlink data, a number of transmission ranks, or amodulation and coding scheme (MCS) level.

Next, the UE checks a transmission location of a demodulation referencesignal (DM-RS) for demodulating the downlink data based on the receivedcontrol information in S1820.

Next, the UE receives, from the base station, a PCRS on at least onesymbol after a transmission symbol of the DM-RS considering the checkedtransmission location of the DM-RS in S1830.

Here, if the DM-RS is transmitted on the same frequency as a frequency,on which the PCRS is transmitted, as a result of checking thetransmission location of the DM-RS by the UE, a sequence of the PCRS maybe used in the same manner as a sequence of the DM-RS.

On the other hand, if the DM-RS is not transmitted on the same frequencyas a frequency, on which the PCRS is transmitted, as a result ofchecking the transmission location of the DM-RS by the UE, a sequence ofthe PCRS may be used in the same manner as a sequence of a DM-RStransmitted on a frequency closest to the frequency on which the PCRS istransmitted.

Further, the PCRS may be transmitted on one or more antenna ports.

If the PCRS is transmitted on multiple antenna ports, frequencies ofPCRSs transmitted on different antenna ports may be different from eachother.

If the PCRS is transmitted on two antenna ports, a PCRS transmitted on afirst antenna port may be transmitted on a frequency corresponding to asubcarrier index #5, and a PCRS transmitted on a second antenna port maybe transmitted on a frequency corresponding to a subcarrier index #6.

A sequence of the PCRS may be generated using a gold sequence.

More specifically, a sequence of the PCRS may be generated via anm-sequence of a gold sequence.

General Device to which the Present Invention is Applicable

FIG. 19 is a block diagram illustrating a configuration of a wirelesscommunication device according to an embodiment of the presentinvention.

Referring to FIG. 19, a wireless communication system includes a basestation 1910 and a plurality of UEs 1920 located within an area of thebase station 1910.

The base station 1910 includes a processor 1911, a memory 1912, and aradio frequency (RF) unit 1913. The processor 1911 implements functions,processes, and/or methods proposed with reference to FIGS. 1 to 18.Layers of a radio interface protocol may be implemented by the processor1911. The memory 1912 is connected to the processor 1911 and storesvarious information for driving the processor 1911. The RF unit 1913 isconnected to the processor 1911 and transmits and/or receives radiosignals.

The UE 1920 includes a processor 1921, a memory 1922, and an RF unit1923. The processor 1921 implements functions, processes, and/or methodsproposed with reference to FIGS. 1 to 18. Layers of a radio interfaceprotocol may be implemented by the processor 1921. The memory 1922 isconnected to the processor 1921 and stores various information fordriving the processor 1921. The RF unit 1923 is connected to theprocessor 1921 and then transmits and/or receives radio signals.

The memory 1912/1922 may be provided inside or outside the processor1911/1921 and may be connected to the processor 1911/1921 by variouswell-known means.

Moreover, the base station 1910 and/or the UE 1920 may have a singleantenna or multiple antennas.

The embodiments described above are implemented by combinations ofcomponents and features of the present invention in predetermined forms.Each component or feature should be considered selectively unlessspecified separately. Each component or feature may be carried outwithout being combined with another component or feature. Moreover, somecomponents and/or features are combined with each other and canimplement embodiments of the present invention. The order of operationsdescribed in embodiments of the present invention may be changed. Somecomponents or features of one embodiment may be included in anotherembodiment, or may be replaced by corresponding components or featuresof another embodiment. It will be apparent that some claims referring tospecific claims may be combined with another claims referring to theother claims other than the specific claims to constitute the embodimentor add new claims by means of amendment after the application is filed.

Embodiments of the present invention can be implemented by variousmeans, for example, hardware, firmware, software, or combinationsthereof. When embodiments are implemented by hardware, one embodiment ofthe present invention can be implemented by one or more ASICs(application specific integrated circuits), DSPs (digital signalprocessors), DSPDs (digital signal processing devices), PLDs(programmable logic devices), FPGAs (field programmable gate arrays),processors, controllers, microcontrollers, microprocessors, and thelike.

When embodiments are implemented by firmware or software, one embodimentof the present invention can be implemented by modules, procedures,functions, etc. performing functions or operations described above.Software code can be stored in a memory and can be driven by aprocessor. The memory is provided inside or outside the processor andcan exchange data with the processor by various well-known means.

While the present invention has been described and illustrated hereinwith reference to the preferred embodiments thereof, it will be apparentto those skilled in the art that various modifications and variationscan be made therein without departing from the spirit and scope of thepresent invention. Thus, it is intended that the present inventioncovers the modifications and variations of this invention that comewithin the scope of the appended claims and their equivalents.

Although the present invention is described with reference to examplesapplying to 3GPP system and 5G system, it can be applied to variouswireless communication systems other than them.

What is claimed is:
 1. A method of transmitting, by a terminal, a phasenoise reference signal in a wireless communication system, the methodcomprising: determining at least one first frequency resource and atleast one first time resource of a demodulation reference signal(DM-RS); mapping the phase noise reference signal to at least one secondfrequency resource and at least one second time resource based on thedetermined at least one first frequency resource and the at least onefirst time resource of the DM-RS; and transmitting, to a base station,the phase noise reference signal on the mapped at least one secondfrequency resource and the at least one second time resource of thephase noise reference signal, wherein the phase noise reference signalis mapped to a plurality of symbols in the at least one second timeresource that are determined based on a location of a DM-RS symbol inthe at least one first time resource of the DM-RS, wherein the pluralityof symbols of the phase noise reference signal are spaced apart fromeach other in time by at least one symbol therebetween, wherein theDM-RS is defined by a DM-RS sequence, and wherein, based on the phasenoise reference signal and the DM-RS being transmitted on an identicalfrequency: the phase noise reference signal is also defined by the DM-RSsequence.
 2. The method according to claim 1, wherein the DM-RS istransmitted on multiple first frequency resources, and wherein the atleast one second frequency resource of the phase noise reference signalis mapped to at least one of the multiple first frequency resources ofthe DM-RS.
 3. The method according to claim 1, wherein the DM-RS istransmitted on multiple first frequency resources at the first timeresource, and wherein the at least one second frequency resource of thephase noise reference signal is mapped to at least one of the multiplefirst frequency resources of the DM-RS at the at least one second timeresource after the at least one first time resource.
 4. The methodaccording to claim 1, wherein the plurality of symbols of the phasenoise reference signal are all located in time after the DM-RS symbol.5. The method according to claim 4, wherein the plurality of symbols ofthe phase noise reference signal are all regularly spaced apart fromeach other by a specific symbol interval.
 6. The method according toclaim 5, wherein the plurality of symbols of the phase noise referencesignal are all regularly spaced apart from each other by the specificsymbol interval such that that phase noise reference signal is mapped toevery other symbol.
 7. The method according to claim 1, wherein afrequency location of the phase noise reference signal in the at leastone second frequency resource is configured differently according to anantenna port that is utilized to transmit the phase noise referencesignal.
 8. The method according to claim 1, wherein the at least onesecond frequency resource of the phase noise reference signal includes afrequency-domain index, and wherein the at least one second timeresource of the phase noise reference signal includes a time-domainindex.
 9. The method according to claim 8, wherein the phase noisereference signal is transmitted on a resource element with thefrequency-domain index and the time-domain index that is not used forthe DM-RS.
 10. The method of claim 1, wherein the DM-RS sequence isgenerated using a Gold sequence.
 11. A user equipment (UE) configured totransmit a phase noise reference signal in a wireless communicationsystem, the UE comprising: a transceiver; at least one processor; and atleast one computer memory operably connectable to the at least oneprocessor and storing instructions that, when executed by the at leastone processor, perform operations comprising: determining at least onefirst frequency resource and at least one first time resource of ademodulation reference signal (DM-RS); mapping the phase noise referencesignal to at least one second frequency resource and at least one secondtime resource based on the determined at least one first frequencyresource and the at least one first time resource of the DM-RS; andtransmitting, to a base station through the transceiver, the phase noisereference signal on the mapped at least one second frequency resourceand the at least one second time resource of the phase noise referencesignal, wherein the phase noise reference signal is mapped to aplurality of symbols in the at least one second time resource that aredetermined based on a location of a DM-RS symbol in the at least onefirst time resource of the DM-RS, wherein the plurality of symbols ofthe phase noise reference signal are spaced apart from each other intime by at least one symbol therebetween, wherein the DM-RS is definedby a DM-RS sequence, and wherein, based on the phase noise referencesignal and the DM-RS being transmitted on an identical frequency: thephase noise reference signal is also defined by the DM-RS sequence. 12.The UE according to claim 11, wherein the DM-RS is transmitted onmultiple first frequency resources, and wherein the at least one secondfrequency resource of the phase noise reference signal is mapped to atleast one of the multiple first frequency resources of the DM-RS. 13.The UE according to claim 11, wherein the DM-RS is transmitted onmultiple first frequency resources at the first time resource, andwherein the at least one second frequency resource of the phase noisereference signal is mapped to at least one of the multiple firstfrequency resources of the DM-RS at the at least one second timeresource after the at least one first time resource.
 14. The UEaccording to claim 11, wherein the plurality of symbols of the phasenoise reference signal are all located in time after the DM-RS symbol.15. The UE according to claim 14, wherein the plurality of symbols ofthe phase noise reference signal are all regularly spaced apart fromeach other by a specific symbol interval.
 16. The UE according to claim15, wherein the plurality of symbols of the phase noise reference signalare all regularly spaced apart from each other by the specific symbolinterval such that that phase noise reference signal is mapped to everyother symbol.
 17. The UE according to claim 11, wherein a frequencylocation of the phase noise reference signal in the at least one secondfrequency resource is configured differently according to an antennaport that is utilized to transmit the phase noise reference signal. 18.The UE according to claim 11, wherein the at least one second frequencyresource of the phase noise reference signal includes a frequency-domainindex, and wherein the at least one second time resource of the phasenoise reference signal includes a time-domain index.
 19. The UEaccording to claim 18, wherein the phase noise reference signal istransmitted on a resource element with the frequency-domain index andthe time-domain index that is not used for the DM-RS.
 20. The UE ofclaim 11, wherein the DM-RS sequence is generated using a Gold sequence.